Broadband Data Signals & Circuits
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Transcript Broadband Data Signals & Circuits
Shunt-Peaking (1)
By connecting an inductor in series with the load
resistor (series connection in shunt with output),
more current is used, for a longer time, to charge
the load capacitance.
EECS 270C / Winter 2013
Prof. M. Green / U.C. Irvine
1
Properties of Shunt-Peaking
Frequency response:
L
R
Z( j ) R
2
1 LCL jCL R
1 j
CL
L
R
Z(s) R
1 sCL R s 2LCL
1 s
Resonant frequency:
1 CL R2
r
1
LCL
L
2
Im s
X
OX
Re s
L = 0:
L ≠ 0:
zero at s = −R/L pole at s = −1/RC
additional pole at
s ≈ −(1/CR + R/L)
EECS 270C / Winter 2013
Prof. M. Green / U.C. Irvine
L
1
No resonance for
2
CL R
2
Shunt-Peaking -- AC Response
L
0.3
CL R 2
CL 38 fF
L = 1.8 nH
BW = 9.4 GHz
R = 400
Use of shunt-peaking
increases small-signal bandwidth
EECS 270C / Winter 2013
L
0.6
CL R 2
L0
BW = 6.3 GHz
L = 3.7 nH
BW = 14.3 GHz
Prof. M. Green / U.C. Irvine
3
Shunt Peaking − Transient Response (1)
Step Response:
Pulse Response (Dtin = 50 ps):
L = 3.7 nH
Dtout = 50.8 ps
ISI = 16 mUI
L = 3.7 nH
td = 6.7 ps
L = 1.8 nH
td = 8.5 ps
L0
td = 13.4 ps
L = 1.8 nH
Dtout = 50.0 ps
ISI = 0 mUI
L=0
Dtout = 48.7 ps
ISI = 26 mUI
EECS 270C / Winter 2013
Prof. M. Green / U.C. Irvine
4
Other Advantages of Shunt-Peaking
• CML load is passive & linear
• Can be shown to be very robust in the presence of parasitic
series resistance and shunt capacitance inductors can be
placed far away from other CML circuit elements.
EECS 270C / Winter 2013
Prof. M. Green / U.C. Irvine
5
Effect of Shunt-Peaking Inductor Parasitics (1)
L
L
L
CP
CP
L
long metal lines
RP
R
R
CL
CL
RP
R
R
CL
CL
• Series resistance RP simply adds to R
• Shunt capacitance CP resonates with L …
EECS 270C / Winter 2013
Prof. M. Green / U.C. Irvine
6
Effect of Shunt-Peaking Inductor Parasitics (2)
L
0.6
CL R 2
ISI (UI) vs. input pulse width
CP 0
L
0
CL R 2
Moderate amount of parasitic capacitance
has similar effect to slightly larger inductor.
L
0.6
CL R 2
ISI (UI) vs. input pulse width
CP 0.2CL
Disadvantages of using passive inductors:
• Consume huge die area
• Difficult to design & model
EECS 270C / Winter 2013
Prof. M. Green / U.C. Irvine
L
0.3
CL R 2
L
0
CL R 2
L
0.3
CL R 2
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Multi-layer Inductors (1)
metal 6
metal 6
d
metal 5
metal 5
d
Distance d between two metal layers is much smaller than lateral distances
(e.g., w, l, s)
EECS 270C / Winter 2013
Prof. M. Green / U.C. Irvine
8
Multi-layer Inductors (2)
2-port representation of coupled inductors:
M k L1L2
i1
+
1
series connection of coupled inductors:
i1
i2
L1
L2
_
M
+
+
1 L1
2
L2 2
_
_
_
+
Passivity constraint: k 1
i2
series (L1 M)i 1 (L2 M)i 2
L M i
1
1
M L2 i 2
i series i i
For metal geometries close to each other,
k is close to unity.
Lseries
series
i series
L1 L2 2M
For L1 = L2 = L, we have: Lseries 2L 2M 2L(1 k) 4L
2
In general, for n layers we have: Lseries n L
Multi-layer inductors are more appropriate for shunt-peaking than resonant structures
due to additional
contact resistance.
EECS 270C / Winter 2013
Prof. M. Green / U.C. Irvine
9
Multi-layer Inductors (3)
Effective Capacitance:
Leffective 4L
Ci
1
1
Ceffective Ci Cj
3
12
Cj
For more details, see:
A. Zolfaghari, A. Chan & B. Razavi, “Stacked inductors and transformers in
CMOS technology,”
IEEE Journal of Solid-State Circuits, vol. 36, April 2001, pp. 620-628.
EECS 270C / Winter 2013
Prof. M. Green / U.C. Irvine
10
Multi-layer Inductors (4)
Area comparison:
metal 6 only
100 x 100
w = 4; s = 2; n = 4
L=2.0 nH
R=6.9
metal 6 over metal 4
46 x 46
w = 4; s = 2; n = 2.5
L=2.0 nH
R=12.5
+
EECS 270C / Winter 2013
Prof. M. Green / U.C. Irvine
11
Active Inductors (1)
Impedance inversion:
Ideal gyrator:
i1
Rgyr
i2
iin
+
+
+
v1
v2
vin
_
_
_
v 2 Rgyr i1
Matrix representation (Z-parameters):
EECS 270C / Winter 2013
Rgyr i1
0 i 2
C
2
Zin Rgyr
sC
v1 Rgyr i 2
v 0
1
v 2 Rgyr
Rgyr
Port 1 exhibits inductance when
port 2 is connected to a capacitance.
Prof. M. Green / U.C. Irvine
12
Active Inductors (2)
Consider common-drain configuration:
i1 applied with port 2 open-circuited:
v2
i2
RG
1
i1
gm
i2 applied with port 1 open-circuited:
+
v2
_
_
1
v1 RG i 2
gm
(Assume RG gm > 1)
v1
i1
+
EECS 270C / Winter 2013
Complete Z-parameters (lossy/active gyrator):
v 1 g R 1 g
G
m
1 m
1 gm
v 2
1 gm
Prof. M. Green / U.C. Irvine
i
1
i 2
13
Active Inductors (3)
Interpretation of non-ideal matrix entries:
+
v 1 g 1 g R i
m
G
1
1 m
1 gm i 2
v 2 1 gm
vin
_
EECS 270C / Winter 2013
Prof. M. Green / U.C. Irvine
14
Active Inductors (4)
Impedance at port 1 with port 2 terminated with transistor Cgs:
At low frequencies (Cgs open) Zsource = 1/gm
At high frequencies (Cgs short) Zsource = RG
Zsource
EECS 270C / Winter 2013
1 1 sCgs RG
gm 1 s Cgs gm
Prof. M. Green / U.C. Irvine
15
Active Inductors (5)
Equivalent circuit:
Leff
Zsource
Cgs RG RG
gm
T
RG
1
gm
+
vin
1
gm
gm
Cgs
1
Cgs RG
gmRG 1
EECS 270C / Winter 2013
Cgs
_
RG
gm
RG
1
gm
Prof. M. Green / U.C. Irvine
16
CML Buffer with Active Inductor Load
Low-frequency gain:
Av
gm 1
W1
gm 2
W2
For shunt peaking:
L 0.3CL R2
W
4
L 1 0.18
W
2.5
L 2 0.18
ISS 400 A
EECS 270C / Winter 2013
Cgs RG
C
0.3 2L
gm 2
gm 2
gm 2RG 0.3
CL
Cgs
Prof. M. Green / U.C. Irvine
17
Active Inductor AC Response
RG = 4k
RG = 2k
RG = 0
EECS 270C / Winter 2013
Prof. M. Green / U.C. Irvine
18
Active Inductor Transient Response (1)
Differential signals:
RG = 0
PW = 97ps
RG = 5k
PW = 100 ps
EECS 270C / Winter 2013
Prof. M. Green / U.C. Irvine
RG = 10k
PW = 104 ps
19
Active Inductor Transient Response (2)
Single-ended signals:
Problem: n-channel load shifts output by Vt.
Vsb > 0; body effects exacerbates this effect..
Single-ended
input
Single-ended
outputs
EECS 270C / Winter 2013
Prof. M. Green / U.C. Irvine
20
Active Inductor Alternate Topology
Alternate topology:
p-channel load exhibits lower Vt
(Vbs = 0)
differential
single-ended
EECS 270C / Winter 2013
Prof. M. Green / U.C. Irvine
21