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High Efficiency Microwave Amplifiers and SiC Varactors Optimized for Dynamic Load Modulation C HRISTER A NDERSSON Microwave Electronics Laboratory Department of Microtechnology and Nanoscience – MC2 May 23, 2013
Thesis contributions
Theory and technology for energy efficient and high capacity wireless systems
Power amplifier analysis
Transistor technology and modeling Wideband design [A]
Transmitter efficiency enhancement
Dynamic load modulation [B, C] Active load modulation [D]
Varactors for microwave power applications
SiC varactors for DLM [E, F] Nonlinear characterization [G] 2
POWER AMPLIFIER ANALYSIS
Transistor technology Simplified model: Baredie 15-W GaN HEMT (Cree, Inc.) Fano limit: GaN HEMT High R opt
and
high X Cds /R opt ratio Ideal choice for wideband high power amplifiers 4
Resistive harmonic loading [A]
Z L (f) = R opt P out = class-B η = 58%
Dimensions: 122 mm x 82 mm.
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Measurements [A] Decade bandwidth performance (0.4 – 4.1 GHz) Pout > 10 W
η
= 40 – 60% DPD linearized to standard ACRL < –45 dBc Envelope tracking candidate 6
Dynamic and active load modulation
TRANSMITTER EFFICIENCY ENHANCEMENT
Dynamic load modulation (DLM) [B,C] Load modulation Restore voltage swing and efficiency Varactor-based DLM Reconfigure load network at signal rate 8
Class-J DLM theory [B] DLM by load
reactance
modulation Ideal for varactor implementation Theory enables analysis Technology requirements Power scaling [B] → [C] Frequency reconfigurability 9
10-W demonstrator @ 2.14 GHz [B] CuW-carrier dimensions: 35 mm x 20 mm.
3-mm GaN HEMT + 2x SiC varactors Efficiency enhancement: 20% → 45% @ 8 dB OPBO 10
100-W demonstrator @ 2.14 GHz [C]
20V 30V 40V
Package internal dimensions: 40 mm x 10 mm.
Fully packaged
24-mm GaN HEMT + 4x SiC varactors
Record DLM output power (1 order of mag.)
Efficiency enhancement: 10-15% units @ 6 dB DPD by vector switched GMP model 17-W WCDMA signal,
η
= 34%, ACLR < –46 dBc 11
β 1
Active load modulation [D]
β 2 , φ
Mutual load modulation
using transistors
Both
transistors must operate efficiently Co-design of MN 1 , MN 2 , and current control functions • Successful examples: Doherty and Chireix Modulate current amplitudes and phase at signal rate 12
β 1
Dual-RF input topology [D]
β 2 , φ
Complex design space – many parameters Linear multi-harmonic calculations (MATLAB) Include transistor parasitics No assumption of short-circuited higher harmonics Optimize for wideband high
average
• efficiency Output: circuit values + optimum current control(s) 13
Verification of calculations [D] 2 x 15-W GaN HEMT design Straightforward ADS implementation – plug in MATLAB circuit values Parasitics and higher harmonics catered for already Good agreement with
complete nonlinear
PA simulation
WCDMA 6.7 dB PAPR (MATLAB) (ADS)
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Measurements [D] Dimensions: 166 mm x 81 mm.
Performance over 100% fractional bandwidth (1.0 – 3.1 GHz) P max = 44 ± 0.9 dBm PAE @ 6 dB OPBO > 45%
Record efficiency bandwidth for load modulated PA
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Varactor-based DLM architecture.
Chalmers MC2 cleanroom.
14-finger SiC varactor (C min = 3 pF).
VARACTORS FOR MICROWAVE POWER APPLICATIONS
Varactor effective tuning range Increasing RF swing decreasing
T eff
Shape of varactor C(V) matters Nonlinear characterization [G] Engineer C(V) to be less abrupt 17
Schottky diode SiC varactors [E,F] Engineer doping profile Higher doping • Lower loss • Higher electric fields
Wide bandgap SiC
High critical electric field SiC varactor performance [E,F] Moderate small-signal tuning range High breakdown voltage High Q-factor Highest tuning range when |RF| > 5 V Used in [B,C,d,g,h] 18
Conclusions Energy efficient wideband power amplifiers Simplified modeling (X Cds /R opt ) Resistive harmonic loading [A] Varactor-based dynamic load modulation [B,C] Active load modulation [D] Varactors for microwave power applications Nonlinear characterization [G] Novel SiC varactor [E,F] • Dynamic load modulation one of many applications Theory and technology for energy efficient high capacity wireless systems 19
Acknowledgment This work has been performed as part of several projects: • • • ”Microwave Wide Bandgap Technology project” ”Advanced III -Nitrides based electronics for future microwave communication and sensing systems” ”ACC” and ”EMIT” within the GigaHertz Centre 20
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Power amplifiers (PA) Final stage amplifier before antenna High power level → efficiency (
η
) critical PA internals FET Input matching network Load matching network
Nonlinear circuit
Propose simplifications to allow linear analysis
These are used in [A-D] 23
Model simplifications [A-D] 15-W GaN HEMT (Cree, Inc.) Linear transistor (constant g m ) Load line in saturated region (no compression) Class-B bias Sinusoidal drive → half-wave rectified current Bare-die parasitics mainly shunt-capacitive Effective ”C ds ” found by load-pull 24
Power amplifiers (PA) Final stage amplifier before antenna High power level → efficiency most critical 25
Typical PA Transistor Microwave frequency FET Input network Gate bias, stability, source impedances (current wave shaping) Load network Drain supply, load impedances (voltage wave shaping) 26
Transistor equivalent circuit Complete model is
complicated
Nonlinear voltage-controlled current source Nonlinear capactiances Feedback Package parasitics
Propose simplifications to allow linear analysis
These are used in [A-D] 27
Comparison [A] 28
PA efficiency and modern signals PA efficiency drops in output power back-off (OPBO) Modern signals High probability to operate in OPBO Average efficiency is low
Need an architecture to restore the efficiency in OPBO
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Dynamic load modulation (DLM) PA efficiency drops in output power back-off (OPBO) Load modulation Restore voltage swing and efficiency Varactor-based DLM Reconfigure load network at signal rate Linearization: RF input + baseband varactor voltage 30
Doherty-outphasing continuum [D] (class-B efficiency)
WCDMA 6.7 dB PAPR
Dual-RF input PA – optimum current control versus power & frequency Classic Doherty impedances & short-circuited higher harmonics
Classic Doherty
transmission line lengths
not best choice
• Adding 90 ° includes outphasing operation and gives higher efficiencies 31
Reality check [D] Realistic circuit Cannot assume short-circuited higher harmonics Must consider transistor parasitics Complicated design space (not suitable for ADS) Linear multi-harmonic calculations (MATLAB) Assume simplified transistor model Optimize circuit values • Relatively cheap calculation • Brute-force evaluation of 14M circuits vs. drive and frequency 32
Nonlinear characterization [G] Active multi-harmonic source/load-pull system Study of an abrupt SiC varactor 33
Power dependent detuning and loss [G] Capacitance and loss increase with RF swing Dependent on varactor and circuit topology 34
Effect of 2nd harmonic loading [G] Q–factor drop due to resonance Relevance in tunable circuit design
Varactors inherently nonlinear devices
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Nonlinear varactor characterization [G] Active multi-harmonic source/load-pull system Study of an
abrupt SiC varactor
Capacitance and loss increase versus RF swing Harmonic loading dependent | RF | | RF | 36